Electronic alignment system for a televison signal tuner

ABSTRACT

An electronic alignment system for a television signal tuner utilizes first and second controllers for generating respective first and second control signals for respective first and second signal processing circuits of a signal processing arrangement, with the first and second signal processing circuits having respective first and second tunable elements responsive to the respective first and second control signals. A deviation range of the first control signal is higher than a deviation range of the second control signal.

BACKGROUND

[0001] 1. Field of the Invention

[0002] The present invention relates to television signal tuners and,more particularly, to an electronic alignment system for a televisionsignal tuner.

[0003] 2. Background Information

[0004] Most, if not all, television signal receivers include a tuner forselecting a particular television signal (channel). Electronic alignmentsystems for television signal tuners have been developed that utilize avoltage signal based on a selected channel. Essentially, a selectedchannel to be tuned provides a channel select signal to a tuning voltagecontroller.

[0005] Electronic alignment has heretofore always required that theradio frequency tuning circuitry of the television signal tuner and thelocal oscillator circuitry of the television signal tuner run on thesame voltage controller/supply. Electronic alignment systems, however,utilize high voltage varactor diodes to receive and utilize the highvoltage developed by the voltage controller to run both the radiofrequency tuning circuitry and the local oscillator circuitry.

[0006] It would thus be desirable to have an electronic alignment systemfor a television signal receiver that utilizes low voltage varactordiodes for at least part of the circuitry.

[0007] It would thus be further desirable to have an electronicalignment system that has radio frequency tuning circuitry and localoscillator circuitry that are independently controlled.

SUMMARY

[0008] In accordance with the invention, there is provided a tuningarrangement. The tuning arrangement includes means for receiving RFsignals, means for outputting a signal, means for processing the RFsignals coupled between the means for receiving RF signals and the meansfor outputting a signal, the means for processing the RF signalsincluding first means for processing the RF signals and second means forprocessing the RF signals respectively. The first and second means forprocessing the RF signals include respective first and second means fortuning the RF signals. The tuning arrangement further includes firstcontrol means for generating a first control signal coupled to the firstmeans for tuning, and second control means for generating a secondcontrol signal coupled to the second means for tuning. A deviation rangeof the first control means is higher than a deviation signal of thesecond control means.

BRIEF DESCRIPTION OF THE DRAWINGS

[0009] In the drawings:

[0010]FIG. 1 is a simplified block diagram of a digital to analogconverter system in accordance with the principles of the subjectinvention;

[0011]FIG. 2 is a block diagram of the digital to analog convertersystem of FIG. 1 particularly depicting a block diagram of the modecontroller;

[0012]FIG. 3 is a representation of the digital to analog convertersystem of FIG. 1 depicting a circuit diagram of the mode controller;

[0013]FIG. 4 is an alternative embodiment of a digital to analogconverter system;

[0014]FIG. 5 is a graph of output voltage versus input code for a threebit digital to analog converter with and without a mode controller;

[0015]FIG. 6 is a block diagram of an electronic alignment system for atelevision signal tuner in which the digital to analog converter systemmay be used; and

[0016]FIG. 7 is an exemplary circuit diagram of the electronic alignmentsystem of FIG. 6.

[0017] Corresponding reference characters indicate corresponding partsthroughout the several views.

DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

[0018] In one form, a tuning arrangement, especially for a televisionsignal tuner, utilizes first and second controllers for generatingrespective first and second control signals for respective first andsecond signal processing circuits of a signal processing arrangement,with the first and second signal processing circuits having respectivefirst and second tunable elements responsive to the respective first andsecond control signals. A deviation range of the first control signal ishigher than a deviation range of the second control signal. In one form,the first and second signal processing circuits are responsive todifferent frequency bands. The first and second controllers may be firstand second voltage controllers and, in one form, the first and secondvoltage controllers may be a tuning controller and a digital to analogconverter. The first and second signal processing circuits may be radiofrequency tuning circuitry, and local oscillator circuitry for the radiofrequency tuning circuitry. The radio frequency circuitry may utilizelow voltage varactors as part of the first tunable element that operateover a first voltage range (deviation range) that is supplied by a lowvoltage digital to analog converter. The local oscillator circuitry mayutilize higher voltage varactors as part of the second tunable elementthat operate over a second voltage range (deviation range) that ishigher than the first voltage range and supplied by a phase lock loop.

[0019] Referring now to the drawings and, more particularly to FIG. 1,there is depicted a simplified block diagram representation of a digitalto analog converter system generally designated 130 in accordance withan aspect of the subject invention. The digital to analog convertersystem 130 includes a digital to analog converter (DAC) 100 and a modecontroller 132. The DAC 100 is representative of any type of DAC. TheDAC 100 is typically an integrated circuit (IC), however, it is notnecessary that the DAC 100 be an IC. Moreover, it should be appreciatedthat while the mode controller 132 is shown as separate from the DAC100, the mode controller 132 may be integral with the DAC 100.Therefore, the DAC system 130 may be all part of an IC.

[0020] The DAC 100 has a voltage supply input 102 that is operative toreceive an operating voltage or voltage supply suitable for allowing theDAC 100 to operate. The voltage of the voltage supply provided to thevoltage supply input 102 of the DAC 100 may vary according to the natureof the IC. Typically, however, such voltage is either five (5) or twelve(12) volts. Of course, the DAC 100 (or DAC system 130 if the DAC system130 is in an integrated IC form) may be different.

[0021] The DAC 100 also has a voltage reference input 104 (V_(ref)) thatis operative to receive a reference voltage (V_(ref)). The referencevoltage (V_(ref)) sets a maximum voltage that the DAC 100 will output. Adata input 106 is provided that is operative to receive an N-bit digitalword (data). The N-bit digital word is converted into a particularanalog voltage. Each different N-bit digital word provides a differentanalog voltage. The DAC 100 is configured to accept a set orpredetermined N-bit digital word. For example, the DAC 100 may be athree bit digital to analog converter meaning that the DAC 100 acceptsonly a three (i.e. N=3) bit digital word from 000 to 111. The input datamay be input serially in which case there is a single data input 106.Alternatively, the input data may be input in parallel. In the parallelinput case there would be a separate line existing for each data bit.For example, a three bit digital to analog converter (accepting a threebits word or data) would have three separate data inputs 106. The numberof bits typically determines the resolution of a DAC. Typical resolutionmay be expressed as 1/(2^(N)−1).

[0022] The DAC 100 also has a an analog output 110 that provides ananalog output voltage dependent upon the reference voltage (as amaximum) input via the voltage reference input 104 and the input data(N-bit digital word) via the data input 106. The DAC 100 provides ananalog output voltage on the analog output 110 which linearly variesfrom zero to the maximum reference voltage as the digital input wordvaries from 0 to 2^(N)−1. The DAC 100 may also be a multiplying DACwherein the magnitude of the analog output is also proportional to someanalog input. The DAC 100 also has a clock input 124 that is operativeto receive a clock signal. The DAC 100 is also connected or coupled toground via a ground connection 126.

[0023] In accordance with an aspect of the subject invention, the modecontroller 132 is connected between the voltage reference input 104 anda reference voltage (V_(cc)). The mode controller 132 has a referencevoltage input 134 that is shown connected to the reference voltage(V_(cc)). The mode controller 132 is operative in two states or modes.In one state, the mode controller 132 allows the DAC 100 to operate at afirst resolution up to a maximum output voltage corresponding to thereference voltage (V_(cc)). In a second state, the mode controllerreduces the maximum output voltage (i.e. to a percentage of V_(cc))while increasing the resolution of the DAC 100. The mode controller 132is also coupled to ground.

[0024] Referring now to FIG. 2, there is depicted the DAC system 130with various elements of the mode controller 132 shown in block form.Particularly, in one form, the mode controller 132 includes voltagedivision circuitry/logic 136 and switch/switching circuitry/logic 138.The voltage division circuitry/logic 136 is connected to the voltagereference source (V_(cc)) via the voltage reference input 134. Theswitch/switching circuitry/logic 138 is connected to ground and isoperative in two states or modes. The first state or mode is an opencircuit condition while the second state or mode is a closed circuitcondition.

[0025] The voltage division circuitry/logic 136 is operative inconjunction with the switch/switching circuitry/logic 138 such that whenthe switch/switching circuitry/logic 138 is in the first state (opencircuit), the voltage division circuitry/logic 136 is operative toprovide one hundred percent (100%) of the maximum reference voltage(V_(cc)) provided to the reference voltage input 104 as an analog outputvoltage at the analog voltage output 110 at a first resolution. Thevoltage division circuitry/logic 1 36 is further operative inconjunction with the switch/switching circuitry/logic 138 such that whenthe switch/switching circuitry/logic 138 is in the second state (closedcircuit), the voltage division circuitry/logic 136 is operative toprovide a percentage of the maximum reference voltage (V_(cc)) providedto the reference voltage input 104 as an analog output voltage at theanalog voltage output 110 at a second resolution that is greater thanthe first resolution.

[0026] The percentage of the maximum reference voltage (V_(cc)) that thevoltage division circuitry/logic 136 provides to the DAC 100(particularly to the voltage reference input V_(ref) 104) is determinedby the circuitry of the voltage division circuitry/logic 136. The firstresolution is calculated by the following equation:

1/(2^(N)−1),

[0027] while the second resolution is calculated by the followingequation:

1/(2^(N+1)−1).

[0028] From these two equations, it can be seen that the resolutiondoubles. In fact, the second resolution is actually slightly greaterthan twice the first resolution depending on the predetermined bit sizeof the input data word for the DAC 100. For example, if the DAC 100 is athree bit DAC then the first resolution is {fraction (1/7)} (i.e. thereare seven steps from zero to the maximum reference voltage) and thus thesecond resolution is {fraction (1/15)} (i.e. there are fifteen stepsfrom zero to the percentage of the maximum reference voltage). Asdescribed below, the percentage of the reference voltage (the maximumreference voltage) that is provided as the maximum analog output voltageis determined by circuit element values. This may be termed a control orswitchover point. While the present invention will be described withrespect to one control point, there may be many control points or theremay be a continuously variable control point.

[0029] It should be noted that the present DAC system provides a secondresolution that is effectively increased. As such, the terms effective,integral and/or fractional resolution may be applied to indicate theincrease in resolution. The subject DAC system thus provides aneffective increase in resolution over a fractional or percentage rangeof the DAC, DAC structure, or DAC system. Stated another way, thesubject invention is akin to providing half a bit of resolution to theDAC, DAC structure, or DAC system over the entire operating range or onebit of resolution for the percentage or fractional operating range.

[0030] Referring to FIG. 3 there is shown an exemplary circuit diagramdepiction of the mode controller 132. Particularly, the voltage divisioncircuitry/logic 136 is shown as a voltage divider 140. In an exemplaryembodiment, the voltage divider 140 consists of a first resistor R1 anda second resistor R2. The first resistor R1 is coupled to a referencevoltage V_(cc). The reference voltage V_(cc) may be ten (10) volts forexample. The second resistor R2 is coupled to the switching circuitry138 here including a switch SW1. The switch SW1 is controlled by aswitch control signal provided on a switch control line 148. The switchSW1 is, in turn, connected to ground. The switch control signal opensand closes the switch SW1.

[0031] The voltage divider 140 is also connected to the referencevoltage V_(ref) input 104 of the DAC 100. Particularly, the referencevoltage V_(ref) input 104 of the DAC 100 is connected between the firstresistor R1 and the second resistor R2. In operation, when the switchSW1 is in an open position (open circuit) as shown in FIG. 3, thevoltage provided to the reference voltage V_(ref) input 104 of the DAC100 is the voltage across the first resistor R1. The voltage across thefirst resistor R1 is the reference voltage supply V_(cc) such that thereference voltage V_(ref) equals V_(cc). When the switch SW1 is in aclosed position (closed circuit), the voltage provided to the referencevoltage V_(ref) input 104 of the DAC 100 is the voltage divided acrossthe first resistor R1 and the second resistor R2 as provided by thefollowing equation:

R1/(R1+R2).

[0032] The reference voltage thus supplied to the DAC 100 is dependentupon the values of the resistors R1 and R2. Thus, the maximum analogoutput voltage is dependent upon the values of R1 and R2 when the switchSW1 is closed.

[0033] When R1=R2, the term R1+R2 may be changed to R1+R1 which is 2R1.Therefore, the equation R1/(R1+R2) may be rewritten as R1/2 R1 whichsimplifies to 1/2R1. Thus when R1=R2, the maximum reference voltage orcontrol point provided to the DAC 100 (and the maximum analog outputvoltage) is ½ or 50% of the reference voltage supply V_(cc). As agenerality, when R1<R2, the control point is less than (<)½V_(cc) or 50%V_(cc). When R1>R2, the control point is greater than (>) ½V_(cc) or 50%V_(cc).

[0034] Resistors R1 and R2 are typically both fixed in value (ohms) butmay be both variable or one fixed and one variable as desired. In thismanner the control point or reference voltage provided to the DAC 100may be controlled rather than fixed in the case of fixed values ofresistor R1 and resistor R2. Thus, the maximum reference voltageprovided to the DAC 100 may be from just over zero to 100% of thereference voltage supply.

[0035] Referring to FIG. 4, there is depicted an alternative embodimenta digital to analog converter (DAC) system generally designated 150. Inthis embodiment, the mode controller 132 is shown as possibly integratedwith the DAC 100 by the dashed lines. It should be appreciated, however,that the mode controller 132 may or may not be integrated with the DAC100. The DAC system 150 operates in the same manner as the DAC system130 described above with the exception that the DAC 100 has a first dataout 1 analog voltage output 110 ₁, a second data out 2 analog voltageoutput 110 ₂, and a third data out 3 analog voltage output 110 ₃. Eachanalog voltage output 110 ₁, 110 ₂, and 110 ₃ provides a separate butequal analog voltage output for the digital input word. Additionally,the DAC system 150 utilizes the voltage V_(cc) for the reference voltageand the operating voltage for the DAC 100.

[0036]FIG. 5 provides a graph 142 of the subject DAC system with a threebit DAC showing output voltage as a function of the three bit digitalinput data. The output voltage ranges from a minimum of zero (0) voltsto a maximum of V_(max) wherein V_(max) may be any voltage butcorresponds to the reference voltage provided to the mode controller 132as the digital input word varies from 000 to 111. V_(max) alsocorresponds to the reference voltage provided to the DAC 100 when theswitch SW1 is in an open state. In the graph 142, the voltage V_(ref1)corresponds to the control point or percentage of maximum referencevoltage when the switch SW1 is closed and the voltage divider 140 isfunctioning.

[0037] In the example depicted in the graph 142, the line 144 representsthe analog output voltage when the switch SW1 is in an open position.For the digital input word 000, the analog voltage output is 0 volts. Asthe digital input word progresses to 111, the analog output voltageincreases to a maximum of V_(max) (i.e. 100% of the reference voltage).The resolution of line 144 may be denoted “X”.

[0038] The line 146 represents the analog output voltage when the switchSW1 is in a closed position. For the digital input word 000, the analogvoltage output is 0 volts. As the digital input word progresses to 111,the analog output voltage increases to a maximum of V_(ref1) (i.e. apercentage of the reference voltage in accordance with the equationR1/(R1+R2)). The resolution of line 144 may be denoted “2X”. It can beseen that the slope of the line 146 is less than the slope of the line144 indicating that there are less voltage increments per step ordigital input word (resolution) between 0 volts and the maximum analogoutput voltage V_(ref1) than the voltage increments per step or digitalinput word (resolution) from 0 volts and the maximum analog outputvoltage V_(max).

[0039] The subject DAC system thus provides switched resolution of anN-bit DAC. Particularly, the subject DAC system allows one to realizethe resolution of N+1 bits over a percentage voltage range of a DACwhile either utilizing an existing N-bit DAC or providing a DACstructure for N bits. Using the three bit example, an R2R ladder networkDAC provides (acts like) eight (8) discrete ladder points includingendpoints. If a 4 bit resolution DAC is needed, the number of ladderpoints would need to be sixteen (16). With the subject invention, a 3bit DAC structure may be used to realize 4 bit performance for aparticular or given range.

[0040] Referring now to FIG. 6, there is depicted a block diagram of anexemplary electronic alignment system for a television signal receiver(television signal) tuner generally designated 200 in which the DACsystem described above may be used. It should be understood, however,that it is not necessary that the DAC system described herein be used inthe electronic alignment system 200. The electronic alignment system 200is operative to receive radio frequency (RF) television signals (RFsignals or input) from an RF television signal source and provide anintermediate frequency (IF) output. Particularly, the electronicalignment system 200 is operative to receive several bands of RFtelevision signals such as VHF (more particularly, two VHF band, band 1and band 2) and UHF television signals and, according to a selectedtelevision channel, provide an IF television channel signal.

[0041] The RF signals are received from an RF signal source such ascable television, an antenna, or the like that may be provided throughan RF input switch or splitter. The received RF signals are input to aU/V (UHF/VHF) splitter 202 that is operative to separate the UHF bandfrom the VHF bands. The U/V splitter 202 receives a control signal BSV(band select VHF) when the selected channel is a VHF band televisionsignal. The control signal BSV is generated by a phase lock loop (PLL)222 here shown in the form of a PLL IC. The control signal BSV is avoltage generated by the PLL 222 in response to a channel selectionsignal.

[0042] The electronic alignment system 200 has a UHF processing portion204, a VHF processing portion 206, a mixer/oscillator portion 214, thePLL 222, and a digital to analog converter (DAC) 224. The UHF processingportion 204 is operative to tune a particular UHF channel (particulartelevision signal) in response to channel selection. The VHF processingportion 206 is operative to tune a particular VHF channel (particulartelevision signal) within a particular VHF band (here one of two VHFbands) in response to channel selection.

[0043] The UHF processing portion 204 includes a single tuned (ST)filter 208 that is connected to the U/V splitter 202 so as to receivethe output of the U/V splitter 202. Particularly, the UHF signals arereceived by the single tuned filter 208 from the U/V splitter 202. Inaccordance with an aspect of the subject invention, the single tunedfilter 208 operates over a zero to five (0-5) volt range. Particularly,the single tuned filter 208 operates over a continuous analog voltagefrom zero to five (0-5) volts. A zero to five volt signal, designatedST, is received from the DAC 224. The DAC 224 produces the zero to fivevolt signal (i.e. the continuous analog 0-5 volt signal) ST in responseto the channel selection signal. The voltage signal ST allows the singletuned filter 208 to tune the selected channel.

[0044] The output of the single tuned filter 208 is provided to an RFamplifier (amp) 210. The RF amplifier 210 is operative to amplify the RFUHF signal from the single tuned filter 208 according to an RF AGC(automatic gain control) signal produced by the television signalreceiver. The RF amplifier 210 is also operative to receive a UHF bandselect signal (BSU) generated by and from the PLL 222. The UHF bandselect signal BSU is generated by the PLL in response to the channelselection signal. The band select signal BSU is essentially an on/offsignal for the RF amplifier 210.

[0045] The output of the RF amplifier 210 is provided to a double tuned(DT) filter 212. In accordance with an aspect of the subject invention,the double tuned filter 212 operates over a zero to five (0-5) voltrange. Particularly, the double tuned filter 212 operates over acontinuous analog voltage from zero to five (0-5) volts. A zero to fivevolt signal, designated PRI, is received from the DAC 224. The DAC 224produces the zero to five volt signal (i.e. the continuous analog 0-5volt signal) PRI in response to the channel selection signal. The PRIvoltage signal allows the first portion of the double tuned filter 212to tune the selected channel. A zero to five volt signal, designatedSEC, is also received from the DAC 224. The DAC 224 produces the zero tofive volt signal (i.e. the continuous analog 0-5 volt signal) SEC inresponse to the channel selection signal. The SEC voltage signal allowsthe second portion of the double tuned filter 212 to tune the selectedchannel.

[0046] The output of the double tuned filter 212 is provided to themixer/oscillator 214, shown in the form of an IC. It should beappreciated that the mixer portion and the oscillator portion may beseparate, but is shown combined. In particular, the output of the doubletuned filter 212 is provided to a mixer 228. A UHF local oscillator (L0)226 has an output connected to the mixer 228. The UHF L0 226 isoperative to receive a local oscillator (L0) tuning voltage signal fromthe PLL 222 and generate a tuned local oscillator signal. The L0 tuningvoltage signal is produced by the PLL in response to the channelselection signal. The L0 tuning voltage signal is an analog voltagesignal from zero to thirty (0-30) volts. The UHF L0 226 also providesfeedback to the PLL 222 in the form of an L0 drive signal.

[0047] The UHF mixer 228 combines or mixes the tuned UHF localoscillator signal from the UHF L0 226 with the output signal (selectedchannel) of the double tuned filter 212. The output of the mixer 228 isprovided to a double tuned intermediate frequency (IF) filter 234. Thedouble tuned IF filter 234 provides its output to an IF amplifier (amp)236. The amplified IF signal (selected television channel) from the IFamplifier 236 is then provided as IF output to the various digital andanalog IF components (not shown) of the television signal receiver orother component.

[0048] The VHF processing portion 206 includes a single tuned (ST)filter 216 that is connected to the U/V splitter 202 so as to receivethe output of the U/V splitter 202. Particularly, the VHF signals arereceived by the single tuned filter 216 from the U/V splitter 202. Inaccordance with an aspect of the subject invention, the single tunedfilter 216 operates over a zero to five (0-5) volt range. Particularly,the single tuned filter 216 operates over a continuous analog voltagefrom zero to five (0-5) volts. A zero to five volt signal, designatedST, is received from the DAC 224. The DAC 224 produces the zero to fivevolt signal (i.e. the continuous analog 0-5 volt signal) ST in responseto the channel selection signal. The voltage signal ST allows the singletuned filter 216 to tune the selected channel.

[0049] Additionally, the single tuned filter 216 is operative to receivea band select signal (BS 1/2) produced by and therefore from the PLL222. The band select signal (BS 1/2) selects one of two VHF bands.Particularly, band select signal (BS 1/2) is an on/off voltage signalderived from the channel selection signal.

[0050] The output of the single tuned filter 216 is provided to an RFamplifier (amp) 218. The RF amplifier 218 is operative to amplify the RFVHF signal from the single tuned filter 216 according to an RF AGC(automatic gain control) signal produced by the television signalreceiver. The RF amplifier 218 is also operative to receive a VHF bandselect signal (BSV) generated by and from the PLL 222. The VHF bandselect signal BSV is generated by the PLL in response to the channelselection signal. The band select signal BSV is essentially an on/offsignal for the RF amplifier 218.

[0051] The output of the RF amplifier 218 is provided to a double tuned(DT) filter 220. In accordance with an aspect of the subject invention,the double tuned filter 220 operates over a zero to five (0-5) voltrange. Particularly, the double tuned filter 220 operates over acontinuous analog voltage from zero to five (0-5) volts. A zero to fivevolt signal, designated PRI, is received from the DAC 224. The DAC 224produces the zero to five volt signal (i.e. the continuous analog 0-5volt signal) PRI in response to the channel selection signal. The PRIvoltage signal allows the first portion of the double tuned filter 220to tune the selected channel. A zero to five volt signal, designatedSEC, is also received from the DAC 224. The DAC 224 produces the zero tofive volt signal (i.e. the continuous analog 0-5 volt signal) SEC inresponse to the channel selection signal. The SEC voltage signal allowsthe second portion of the double tuned filter 220 to tune the selectedchannel.

[0052] Additionally, the double tuned filter 220 is operative to receivethe band select signal (BS 1/2) produced by and therefore from the PLL222. The band select signal (BS 1/2) selects one of two VHF bands.Particularly, band select signal (BS 1/2) is an on/off voltage signalderived from the channel selection signal. The band select signal (BS1/2) is the same as provided to the single tuned filter 216.

[0053] The output of the double tuned filter 220 is provided to themixer/oscillator 214, shown in the form of an IC. It should beappreciated that the mixer portion and the oscillator portion may beseparate, but is shown combined. In particular, the output of the doubletuned filter 220 is provided to a mixer 232. A VHF local oscillator (L0)230 has an output connected to the mixer 232. The VHF L0 230 isoperative to receive a local oscillator (L0) tuning voltage signal fromthe PLL 222 and generate a tuned local oscillator signal. The L0 tuningvoltage signal is produced by the PLL in response to the channelselection signal. The L0 tuning voltage signal is an analog voltagesignal from zero to thirty (0-30) volts. The VHF L0 230 also providesfeedback to the PLL 222 in the form of an L0 drive signal.

[0054] The VHF mixer 232 combines or mixes the tuned VHF localoscillator signal from the VHF L0 230 with the output signal (selectedchannel) of the double tuned filter 220. The output of the mixer 232 isprovided to the double tuned intermediate frequency (IF) filter 234. Thedouble tuned IF filter 234 provides its output to the IF amplifier (amp)236. The amplified IF signal (selected television channel) from the IFamplifier 236 is then provided as IF output to the various digital andanalog IF components (not shown) of the television signal receiver orother component.

[0055] The channel selection signal is typically, but not necessarily,produced by the television signal receiver having the electronicalignment system 200 in response to user input. The channel selectionsignal is provided to the DAC 224 and the PLL 222. While other mannersof providing the channel selection signal are contemplated, theelectronic alignment system 200 is shown utilizing the I²C (or IIC)configuration/protocol. As such, an I²C clock line and an I²C data lineis shown connected to the DAC 224 and the PLL 222. Both the PLL 222 andthe DAC 224 produce an analog voltage signal continuously ranging fromzero (0) to a maximum voltage which, in the case of the DAC 224 is five(5) volts, and in the case of the PLL 222 is thirty (30) volts.

[0056] Moreover, it should be noted that while the electronic alignmentsystem or electronic tuner presented herein is described using five voltvaractors for the RF (radio frequency) section and thirty volt varactorsfor the L0 (local oscillator) section, other voltage varactors may beused. According to the principles of the subject invention, the voltagesupply (and thus the varactor(s)) for the RF section and the voltagesupply (and thus the varactor(s)) for the L0 section are just different.Such difference preferably manifests itself as the voltage supply andthe varactor(s) (i.e. varactor voltage capacity) for the RF section aslower than the voltage supply and the varactor(s) (i.e. varactor voltagecapacity) for the L0 section. Thus, for example, the RF section may usea twelve volt supply/varactor(s) while the L0 section may use athirty-three volt supply/varactor(s). Further, the supply and/orvaractor voltage may or may not be a function of one another.

[0057] Referring to FIG. 7, there is depicted an exemplary circuitdiagram for the block diagram for the electronic alignment system 200 ofFIG. 6. It should be appreciated that the circuit of FIG. 7 works in themanner described with respect to FIG. 6. Therefore, only certainportions of the circuit 200 will be described with particularity.Initially, the RF IN is split by the splitter 202, particularly by thecapacitor C0 and the inductor L0. The UHF portion branches through thecapacitor C0 while the VHF portion branches through the inductor L0. Theresistor R0 provides charge buildup protection/elimination and/orlightening protection. The resistor R0 is coupled to the inductor L0 andground.

[0058] As indicated above, the UHF section 204 has a single tuned filter208 that is varactor voltage controlled. The single tuned filter 208includes series inductors L8 and L9 that is in parallel with a lowvoltage (i.e. 0-5 volts) varactor (varactor diode) VR7 and a capacitorC7. The series inductors L8 and L9 and parallel varactor VR7 andcapacitor C7 are connected to ground. The tuning voltage signal ST isprovided through a resistor R4 to the node between the varactor VR7 andthe capacitor C7. The single tuned filter 208 changes in electricalcharacteristics based on the voltage applied to the varactor VR7. Inthis manner, the single tuned filter 208 may tune a particular UHFchannel based on the input voltage signal ST.

[0059] The single tuned filter 208 is coupled to the RF amplifier 210via a capacitor C9. The amplifier 210 includes a dual gate N channelmetal oxide semiconductor (MOS) field effect transistor (FET) T2. Thecapacitor C9 is coupled to one gate of the transistor T2, while theother gate of the transistor T2 receives the RF AGC signal. The sourceof the transistor T2 is connected to ground. An inductor L10 is coupledto the drain of the transistor T2. The inductor L10 is coupled to thePLL 222 in order to receive the UHF band select (BSU) signal whenappropriate. Application or non-application of the BSU signal causes theamplifier to either work or not resulting in conduction to let thesignal through or non-conduction to not let the signal through. The RFamplifier 210 is coupled to the double tuned filter 212 via a capacitorC10.

[0060] The double tuned filter 212 includes a first stage 250 that is inmutual conductance relationship with a second stage 252 via respectiveinductors L11 and L12. The first stage 250 includes a low voltage (0-5volts) varactor VR8 that is coupled at one end to the capacitor C10 andat the other end to a capacitor C11 such that the varactor VR8 and thecapacitor C11 are in series. The series varactor VR8 and capacitor C11are in parallel with the inductor L11. The tuning voltage signal PRI isprovided through a resistor R5 to the node between the varactor VR8 andthe capacitor C11. The first stage 250 changes in electricalcharacteristics based on the voltage applied to the varactor VR8.

[0061] The double tuned filter 212 includes a second stage 252 that isin mutual conductance relationship with the first stage 250 via therespective inductors L11 and L12. The second stage 252 includes a lowvoltage (0-5 volts) varactor VR9 that is coupled at one end to theinductor L12 and at the other end to a capacitor C12 such that thevaractor VR9 and the capacitor C12 are in series while the varactor VR9and the capacitor C12 are in parallel with the inductor L12. The tuningvoltage signal SEC is provided through a resistor R5 to the node betweenthe varactor VR9 and the capacitor C12. The second stage 252 changes inelectrical characteristics based on the voltage applied to the varactorVR9. In this manner, the double tuned filter 212 may tune a particularUHF channel based on the input voltage signals PRI and SEC. The outputof the double tuned filter 212 is provided through a capacitor C13 tothe mixer/oscillator IC 214.

[0062] As indicated above, the VHF section 206 has a single tuned filter216 that is varactor voltage controlled. The single tuned filter 216includes an inductor L1. A low voltage (i.e. 0-5 volts) varactor(varactor diode) VR1 is coupled at one end to the inductor L1 and at theother end to a capacitor C1 such that the varactor VR1 and the capacitorC1 are in series. The series varactor VR1 and the capacitor C1 are inparallel with series inductors L2 and L3. The capacitor C1 and theinductor L3 are connected to ground. The tuning voltage signal ST isprovided through a resistor R4 to the node between the varactor VR1 andthe capacitor C1. The single tuned filter 216 changes in electricalcharacteristics based on the voltage applied to the varactor VR1. Inthis manner, the single tuned filter 216 may tune a particular VHFchannel based on the input voltage signal ST.

[0063] The single tuned filter 216 is further responsive to the bandselect signal BS1 in order to change the band tuning of the single tunedfilter 216. The single tuned filter 216 further includes a low voltage(0-5 volts) varactor VR2 in series with a capacitor C2. The signal BS1is applied between the varactor VR2 and the capacitor C2. The seriesvaractor VR2 and capacitor C2 are disposed in parallel with the inductorL3.

[0064] The single tuned filter 216 is coupled to the RF amplifier 218via a capacitor C8. The amplifier 218 includes a dual gate N channelmetal oxide semiconductor (MOS) field effect transistor (FET) T1. Thecapacitor C8 is coupled to one gate of the transistor T1, while theother gate of the transistor T1 receives the RF AGC signal. The sourceof the transistor T1 is connected to ground. An inductor L4 is coupledto the drain of the transistor T1. The inductor L4 is coupled to the PLL222 in order to receive the VHF band select (BSV) signal whenappropriate. Application or non-application of the BSV signal causes theamplifier to either work or not resulting in conduction to let thesignal through or non-conduction to not let the signal through. The RFamplifier 218 is coupled to the double tuned filter 220.

[0065] The double tuned filter 220 includes a first stage 254 that is inmutual conductance relationship with a second stage 256 via two sets ofrespective inductors L4 and L6, and L5 and L7. The first stage 254includes a low voltage (0-5 volts) varactor VR3 that is coupled at oneend to the amplifier 218 and at the other end to a capacitor C3 suchthat the varactor VR3 and the capacitor C3 are in series. The seriesvaractor VR3 and capacitor C3 are in parallel with the series inductorsL4 and L5. The tuning voltage signal PRI is provided through a resistorR2 to the node between the varactor VR3 and the capacitor C3. The firststage 254 changes in electrical characteristics based on the voltageapplied to the varactor VR3.

[0066] The first stage 254 of the double tuned filter 220 is furtherresponsive to the band select signal BS1 in order to change the bandtuning of the first stage 254 of the double tuned filter 220. The firststage 254 further includes a low voltage (0-5 volts) varactor VR4 inseries with a capacitor C4. The signal BS1 is applied between thevaractor VR2 and the capacitor C2. The series varactor VR2 and capacitorC4 is disposed in parallel with the inductor L5.

[0067] The double tuned filter 220 includes a second stage 256 that isin mutual conductance relationship with the first stage 254 via therespective inductor pairs L4 and L6, and L5 and L7. The second stage 256includes a low voltage (0-5 volts) varactor VR6 that is coupled at oneend to the inductor L6 and at the other end to a capacitor C6 such thatthe varactor VR6 and the capacitor C6 are in series while the varactorVR3 and the capacitor C6 are in parallel with the inductors L6 and L7.The tuning voltage signal SEC is provided through a resistor R3 to thenode between the varactor VR6 and the capacitor C6. The second stage 256changes in electrical characteristics based on the voltage applied tothe varactor VR6.

[0068] The second stage 256 of the double tuned filter 220 is furtherresponsive to the band select signal BS1 in order to change the bandtuning of the second stage 256 of the double tuned filter 220. Thesecond stage 256 further includes a low voltage (0-5 volts) varactor VR5in series with a capacitor C5. The signal BS1 is applied between thevaractor VR5 and the capacitor C5. The series varactor VR5 and capacitorC5 is disposed in parallel with the inductor L7. In this manner, thedouble tuned filter 220 may tune a particular VHF channel of aparticular band based on the input voltage signals PRI and SEC and theband select signal BS1. The output of the double tuned filter 220 isprovided through a capacitor C7 to the mixer/oscillator IC 214.

[0069] The mixer/oscillator 214 receives either the BSV or BSU controlsignals in order to select which local oscillator to utilize. Further,the PLL 222 is coupled to the mixer oscillator 214 such that a tuningvoltage derived from the channel selection signal, is provided to a UHFlocal oscillator (LO) tuning section 238 and a VHF local oscillator (LO)tuning section 240. The UHF LO tuning section 238 is operative toprovide tuning based on the channel selection. The VHF LO tuning section240 is operative to provide tuning based on the channel selection.

[0070] The UHF LO tuning section 238 includes a high voltage (0-30volts) varactor VR10 that is in series with a capacitor C14. The seriesvaractor VR10 and capacitor C14 are disposed in parallel with aninductor L13. The 0-30 volt tuning signal from the PLL 222 is providedthrough a resistor R9 to the node between the varactor VR1 and thecapacitor C14. This provides a tuned signal to the mixer/oscillator 214for UHF tuning.

[0071] The VHF L0 tuning section 240 includes a high voltage (0-30volts) varactor VR11 that is in series with a capacitor C15. The seriesvaractor VR11 and capacitor C15 are disposed in parallel with aninductor pair L14 and L15. The 0-30 volt tuning signal from the PLL 222is provided through a resistor R10 to the node between the varactor VR11and the capacitor C15. Tapped between the inductor pair L14 and L15 isband select circuitry operative in response to the band select signalBS1. The band select signal is provided between a varactor VR12 and acapacitor C16. This provides a tuned signal to the mixer/oscillator 214for VHF tuning.

[0072] As indicated herein, the subject DAC system described above ispreferably used in the exemplary electronic alignment system for atelevision signal receiver (television signal) tuner due to the tuningcharacteristics of varactor diodes (varactors). Particularly, the tuningcharacteristics of a varactor diode is such that it has a more rapidchange of capacitance (and frequency) in the lower voltage range. As aresult, this more rapid change sets the necessary resolution (i.e. agreater resolution). In the upper voltage range, however, the change ismuch slower, allowing for a lower resolution. While a higher resolutionDAC (i.e. more bits) may be used, a higher resolution DAC is moreexpensive. Moreover, a higher resolution DAC would then waste theresolution at the higher voltages (and frequencies within a tuningband). The present switched resolution DAC thus allows one to use thelower resolution DAC and gain the advantage of the higher resolutiononly in the needed range.

[0073] While this invention has been described as having a preferreddesign, the present invention can be further modified within the spiritand scope of this disclosure. This application is therefore intended tocover any variations, uses, of adaptations of the invention using itsgeneral principles. Further, this application is intended to cover suchdepartures from the present disclosure as come within known or customarypractice in the art to which this invention pertains and which fallwithin the limits of the appended claims.

What is claimed is:
 1. A tuning arrangement comprising: a source of RFsignals; a signal output point; a signal processing arrangement coupledbetween said source of RF signals and said signal output point, saidsignal processing arrangement including first and second signalprocessing circuits respectively; said first and second signalprocessing circuits including respective first and second tunableelements; a first controller coupled to said first tunable element forgenerating a first control signal; a second controller coupled to saidsecond tunable element for generating a second control signal; and adeviation range of said first control signal is higher than a deviationsignal of said second control signal.
 2. The tuning arrangement of claim1, wherein said second signal processing circuit comprises firstfrequency band signal processing circuitry and second frequency bandprocessing circuitry.
 3. The tuning arrangement of claim 1, wherein saidfirst signal processing circuit comprises oscillator circuitry, and saidsecond signal processing circuit comprises RF tuning circuitry.
 4. Thetuning arrangement of claim 1, wherein said first controller comprises aphase lock loop and said second controller comprises a digital to analogconverter.
 5. The tuning arrangement of claim 1, wherein said firsttunable element comprises first and second local oscillator circuitsresponsive to said first control signal, and said second tunable elementcomprises first and second tunable filter elements responsive to saidsecond control signal.
 6. The tuning arrangement of claim 5, whereinsaid first tunable filter elements comprises a first single tunedtunable filter and a first double tuned tunable filter responsive tosaid deviation range of said second control signal to pass a selectedfrequency, and said second tunable filter elements comprises a secondsingle tuned tunable filter and a second double tuned tunable filterresponsive to said deviation range of said second control signal to passa selected frequency.
 7. The tuning arrangement of claim 6, wherein saidfirst and second single tuned tunable filters each includes a varactorresponsive to said deviation range of said second control signal, andsaid first and second double tuned tunable filters each includes twovaractors each of which is separately responsive to said deviation rangeof said second control signal.
 8. A tuning arrangement comprising: meansfor receiving RF signals; means for outputting a signal; means forprocessing the RF signals coupled between said means for receiving RFsignals and said means for outputting a signal, said means forprocessing the RF signals including first RF signal processing means forprocessing the RF signals and second RF signal processing means forprocessing the RF signals respectively; said first RF signal processingmeans including first means for tuning the RF signals; said second RFsignal processing means including second means for tuning the RFsignals; first control means for generating a first control signalcoupled to said first means for tuning; second control means forgenerating a second control signal coupled to said second means fortuning; and wherein a deviation range of said second control means ishigher than a deviation signal of said first control means.
 9. Thetuning arrangement of claim 8, wherein said first RF signal processingmeans for processing the RF signals comprises means for processing afirst frequency band signal and means for processing a second frequencyband signal.
 10. The tuning arrangement of claim 8, wherein said secondmeans for processing the RF signals comprises mixing means.
 11. Thetuning arrangement of claim 8, wherein said second control meanscomprises a phase lock loop means and said first control means comprisesa digital to analog converter.
 12. The tuning arrangement of claim 8,wherein said second means for tuning comprises first and second meansfor generating a local oscillator signal responsive to said secondcontrol signal, and said first means for tuning comprises first andsecond means for tunably filtering the RF signals.
 13. The tuningarrangement of claim 12, wherein said first means for tunably filteringthe RF signals comprises a first single tuned tunable filter means and afirst double tuned tunable filter means responsive to said deviationrange of said first control signal to pass a selected frequency, andsaid second means for tunably filtering the RF signals comprises a firstsingle tuned filter means and a second double tuned tunable filter meansresponsive to said deviation range of said first control signal to passa selected frequency.
 14. The tuning arrangement of claim 13, whereinsaid first and second single tuned tunable filter means each includes avaractor responsive to said deviation range of said first controlsignal, and said first and second double tuned tunable filter means eachincludes two varactors each of which is separately responsive to saiddeviation range of said first control signal.
 15. In a television signalreceiver, a method of tuning comprising: receiving a plurality of RFsignals; generating by a first controller a first control signal havinga first deviation range; tuning the plurality of RF signals according tosaid first control signal to obtain a selected one of said RF signals;generating by a second controller a second control signal having asecond deviation range that is higher than the first deviation range;generating a local oscillator signal according to the second controlsignal; and mixing said local oscillator signal with said selected oneof said RF signals to generate an IF signal.
 16. The method of claim 15,wherein the step of generating by a first controller a first controlsignal having a first deviation range includes the step of generating bya first controller comprising a digital to analog converter a firstcontrol signal having a first deviation range.
 17. The method of claim15, wherein the step of generating by a second controller a secondcontrol signal having a second deviation range includes the step ofgenerating by a second controller comprising a phase lock loop a secondcontrol signal having a second deviation range.
 18. The method of claim15, wherein the step of tuning the plurality of RF signals according tosaid first control signal includes the step of selecting via one offirst and second single tuned tunable filter and double tuned tunablefilter pairs one of said RF signals according to said first controlsignal.
 19. The method of claim 18, wherein the step of selecting viaone of first and second single tuned tunable filter and double tunedtunable filter pairs one of said RF signals according to said firstcontrol signal includes the step of selecting via one of first andsecond single tuned tunable filter via a varactor diode and double tunedtunable filter via dual varactor diodes pairs one of said RF signalsaccording to said first control signal.